• 专利附录
  • 专利说明
  • 权利要求
  • 类似技术
  • 同族专利
  • 引用文献
  • 法律状态
  • 优先权
    • 专利摘要:
    A self-oscillating power-supply circuit comprises between two power-supply terminals (1, 2) the series arrangement of the primary winding (n1) of a transformer, a first transistor (T1), a first resistor (R1), and a second series arrangement of the secondary winding (n2) and a first diode (D1), with terminals (2, 4) for the connection of a battery (B) and, via a switch (S1), a motor (M). The secondary winding (n2) is connected to the base of the first transistor (T1) via the series arrangement of a second resistor (R2), a first capacitor (C1) and a third resistor (R3), a first zener diode (D2) being arranged between the third resistor (R3) and the first resistor (R1). The ends of the first resistor (R1) are coupled to the inputs (16, 17) of a switching amplifier (15) for turning off the first transistor (T1) at a specific voltage across the first resistor (R1). In order to achieve change-over from a normal charging current to a trickle-charging current at a specific battery voltage and in order to power the motor (M) with a constant voltage which is independent of the load, the circuit further has switching means comprising the series arrangement of a fourth resistor (R4), a second transistor (T2) and a fifth resistor (R5), the base of the second transistor (T2) being coupled to the node (6) between the first capacitor (C1) and the second resistor (R2), to which a second diode (D3) is arranged in parallel.
    公开号:SU1729305A3
    申请号:SU904743002
    申请日:1990-02-12
    公开日:1992-04-23
    发明作者:Эгберт Альгра Йоханнес；Браувер Джерри
    申请人:Н.В.Филипс Глоэлампенфабрикен (Фирма)；
    IPC主号:
    专利说明:

    formed by a sequence of two nickel-cadmium elements. The motor M, for example, a razor can be connected in parallel with battery B using switch S1. A sequence of devices consisting of a resistor R2. a capacitor C1 and a resistor R3 are installed between the node 5 formed by the secondary winding N2 and the diode D1 and the base of the transistor T1. A Zener diode D2 is installed between the node 6 formed by the capacitor C1 and the resistor R3, and the terminal of the resistor R1 closest to terminal 4. The base of the transistor T1 is connected to the collector of the transistor T1 using a starting resistor R6. This resistor can be alternately connected to the input terminal 1. The terminals 3 and 4 of the resistor R1 are connected to the inputs 7 and 8 of the first switching means 9. which has an output 10. connected to the base of the transistor T1. In this case, the switching means 9 contains a transistor TZ. the emitter of which is connected to the input 7, the base to the input 8, and the collector to the second power terminal 2 through a sequence of devices consisting of two resistors R7 and R8. The node formed by these two resistors is connected to the base of the TZ transistor. the emitter of which is connected to the second power terminal, and the collector of which is connected to both output 10 and input 8 via capacitor C2. The TZ and T4 transistors together with the resistors R7 and R8 and the capacitor C2 form the Schmitt dynamic trigger circuit. A sequence of devices consisting of a resistor R4, a collector-emitter junction of a transistor T4, and a resistor R5. installed between the first input 7 and power terminal 2. The transistor T4 its base is connected to the node 11 formed by the resistor R2 and the capacitor C1. Diode D3 is installed parallel to resistor R2. The emitter of transistor T4 is connected to pin 4 of resistor R1 by means of Zener diode D4. The diode D4 is installed in series with the stabilitron D4, their anodes or cathodes face each other.
    The operation of the circuit can be explained as follows, if for some time the influence of the transistor T4, resistor R5 and diode 03 is neglected. The switch is assumed to be open and the circuit provides only the charging current for battery B. If there is an input voltage between terminals 1 and 2 through the base of the transistor T1, a small current will flow through the starting resistor R6 in such a way that the said transistor will be partially transferred to the conducting state. The resulting current through the primary winding N1 will cause
    the increase in the voltage on the secondary winding N2 so that the transistor T1 will open even more as a result of the positive feedback
    through R2 resistor. capacitor C1 and resistor R3. As a result of the continued positive feedback, the transistor T1 quickly saturates. The voltage on the secondary winding N2 is proportional to the voltage on the primary winding N1 and, therefore, the input voltage. The base current of the T1 transistor will therefore be independent of the input voltage. This will lead to an increase in the closing delay of the T1 transistor, which occurs in the case of an increase in the input voltage, which will lead to an undesirable increase in the charging current of the battery B. However, the base current of the T1 transistor causes
    0, the voltage drop across resistor R2 is such that the voltage at node 6 reaches the voltage across the Zener diode D2. As a result, the base current of the transistor T1 becomes independent of the input voltage, so
    5 that the entire transistor T1 is equally saturated and the closing delay is therefore independent of the input voltage. The base current is set using a resistor R3. On the contrary. the anode of the Zener diode D2 can be connected directly to the emitter of the first transistor T1. However, the diagram of FIG. 1 has the advantage that the base current of the transistor at the beginning of the forward interval is the largest, so that the transistor T1 is rigidly open and the forward run interval is short. In addition, in the above scheme, the T1 transistor is less deeply saturated by the end of
    0, the forward path is so long that this transistor can close more quickly. After opening the transistor T1 as described above, the current through the primary winding N1 increases linearly with the time duration of the forward path. The voltage at node 5 is positive, so that diode D1 is closed. The primary current is converted to a voltage across the resistor R1, and this voltage is applied to a sequence of devices consisting of the base-emitter junction of the transistor T2 and the zener diode D4. When the voltage across the Zener diode is reached, the voltage at the base of the transistor
    5 T2 is kept constant. As the primary current increases, the voltage across the resistor R4 will also increase until the boundary voltage of the transistor T2 is reached and the transistor T2 opens. The collector current of the transistor T2 translates the transistor TZ into a conducting state through resistors R7 and R8 in such a way that the base current moves away from transistor T1. The voltage drop arising on the collector of the TZ transistor is transmitted to the base of the transistor T2 through the capacitor C2, so that the latter is quickly transferred to the full conduction state.
    Since there is no primary current, the polarity of the voltage on the secondary winding N2 is inverse, so that the diode D2 is open. The energy stored in the transformer during the forward stroke interval is fed to battery B as the charging current during the so-called reverse stroke. This current is reduced to zero as a linear function of time. During the reverse stroke, the voltage at the terminal of the secondary winding N2 is negative and equal to the voltage across the diode D1. At the end of the reverse stroke, the voltage on the secondary winding N2 becomes equal to OV, so the voltage at node 5 becomes equal to the battery voltage. This positive voltage drop at node 5 ensures that after some time the next forward stroke interval due to positive feedback through R2, C1 and R3 begins.
    In the manner described above, a battery of cells can be charged relatively quickly with a relatively large current, for example, 2C - current (1, 2 A) in the case of two 1C NlCa charged cells of 1.2 V each.
    In order to prevent battery damage due to overcharging, the power supply circuit is equipped with very simple switching means that replace the normal charging current with the jet current. as soon as the battery cells reach their fully charged state. These switching means include a transistor T2, resistors R4, R5 and R11, a diode D3 along with a resistor R2, a capacitor C1 and a zener diode D2. Switching means works as follows.
    While the battery cells are charging, the voltage at the emitter of the transistor T2 is at least equal to the battery voltage during the forward running interval. The voltage at the base of the transistor T4 is equal to the sum of the battery voltage, the breakdown voltage of the Zener diode D2 and the voltage on the capacitor C1, the output of which is 11, closest to the output 5 of the secondary winding N2, which is positive progress is positive relative to
    pin 6, therefore, the sum of the emitter-base voltages of the transistors t2 and p4 is negative, so that transistor t2 is closed during the forward running interval. Since in this situation the current does not flow into the base of transistor T4, there is no drop in voltage across R11. At the beginning of the reverse stroke, the polarity of the voltage on the secondary winding N2 is reversed so that diode D1 opens and the voltage at node 5 becomes equal to the negative supply voltage (ground) minus one voltage drop across the diode.
    As a result, capacitor C1 is recharged through Zener diode D2 and diode D3. The voltage at node 11, which is connected to the base of transistor T4 through resistor R11, is therefore. 0V, The voltage at pin 6 of capacitor C1 is set to a value equal to the battery voltage minus one voltage drop across the diode, generated by the zener diode D2. which works like a diode during a flyback. The voltage at the emitter of the transistor T2 is equal to the battery voltage. The potential difference between the emitter of the transistor T2 and the node 11 is also equal to the battery voltage. Resistor R11 now works as a current-limiting resistor for the base of transistor T4 in such a way that the sum of the two voltages of the base-emitter can not become too large. In particular, at the beginning of the reverse stroke, the voltage on the battery is substantially higher than the actual voltage on the battery as a result of the voltage drop that occurs on the internal resistance of the battery by means of charging current. Under normal conditions, the voltage at the base-emitter junctions of the transistors T2 and T4 at the beginning of the reverse stroke is above two drops of the base-emitter voltage, so T2 and T4 will be in a conducting state. As long as the transistor T4 holds sufficient current, resistor 4 will maintain a corresponding base-emitter voltage drop across transistor T2 to maintain its conductive state and through transistor T4, the closed state of the switching transistor T1. This prevents the transistor T1 from reopening after closing.
    In order to eliminate the effect of the internal resistance on the battery voltage, determining the adequacy of the battery charge and the need to replace the jet charge is done by determining the voltage on the battery at the end of the reverse stroke when the charging current is
    equals zero. At the end of the reverse stroke, the voltage on the secondary winding N2 becomes zero and the voltage on node 5 formed by the secondary winding and diode D1 jumps from zero to battery voltage. This voltage drop is not monitored immediately by the node 11 formed by the capacitor G1 and the resistor R2, so the voltage at the base of the transistor T4 will not immediately change at the end of the reverse stroke. Consequently, a voltage equal to the voltage across the capacitor C1 will appear between the emitter of the transistor T2 and the base of the transistor T4. During the return stroke, the capacitor is charged before the battery voltage minus the voltage drop across the diode D2 so that the voltage across the capacitor is proportional to the battery voltage. When the cells are appropriately charged, the voltage of the capacitor C1 will be so high that the transistors T4 and T2 will be conductive.
    Since Zener D2 operates as a diode and remains conductive, the voltage at the terminal of the capacitor C1 nearest to Zener diode D2 remains equal to the difference between the battery voltage and the voltage at Zener diode D2. As long as the switching transistor T1 remains closed, the node 5 will remain under battery voltage. The output of the capacitor C1 nearest to this node then gradually takes the value of this voltage, the time constant is set by the RC time of the circuit containing R2 and C1. As long as the voltage is high enough, the transistors T2 and T4 remain conductive. As a result, the transistor T1 remains closed, delaying the start of the next upstream interval. The T4 transistor at the time is held to the necessary extent in the conducting state. If we neglect the slight voltage drop across the resistor R1 and the collector-emitter voltage of the transistor T4, then the voltage across the resistors R4 and R5 will be equal to the battery voltage. The transistors T2 remain in the conductive state until the voltage on the capacitor C1 decreases so much that the transistor T4 closes and the voltage on the resistor R4 becomes too low to maintain the conductivity of the transistor T2. The next upstream interval can now begin. At least one base-emitter voltage is available on C1, so that T1 is immediately transferred to the conducting state at the beginning of the forward stroke interval. In this way.
    when a certain voltage is reached the battery and cells are properly charged, several forward runs are delayed after each
    forward stroke interval, whereby
    decreases the average charge current. So
    in a way it is possible to change, for example, the current
    charge 1.2 A per jet current charge 0.12 A.
    Fig. 2a shows schematically a primary charging current of a jet type, the suppressed forward stroke intervals are shown by a dotted line. Figure 2a shows schematically the average charge current as a function of battery voltage.
    5 In the diagram of the device of FIG. 1, the replacement point of the normal charge current to the jet charge current can be located at any desired voltage, for example, the motor's working voltage.
    0 In this case, the power supply circuit will operate as a constant voltage source when the switch S1 is closed, which, depending on the engine load, is able to supply output current that changes 5 s from the jet charging current to the normal charging current. This prevents the power supply voltage of the engine and, therefore, the rotational speed of the engine from increasing with increasing load,
    0 The described scheme is characterized by a steep dependence between the current generated and the voltage in such a way that, in the event of a change in the engine load, the current flowing to it rapidly changes within
    5 0.12 Au and 1.2 A and the rotational speed of the engine remains constant.
    Fig. 3 shows a second embodiment of the power circuit according to the invention. Identical parts are marked the same.
    0 by digital reference as in FIG. 1. In this embodiment, the network voltage is applied to the bridge rectifier through two terminals 12 and 13. The rectified voltage is smoothed by a filter,
    5 includes inductance L1 and two capacitors C3 and C4 and then applied to the input terminal 1. A sequence of devices consisting of an Zener diode D b is installed
    0 parallel to the primary winding for suppressing voltage surges when current is cut through the primary winding.
    A voltage divider containing resistors R10 and R-11 is installed between the emitter and the base of transistor T4; resistor R10 is a suitable variable resistor. This voltage divider produces a voltage at which the transistor T4 is transformed into a conducting state and, therefore, a voltage at which
    There is a change of the normal charge current to the jet charge current, precisely determined.
    In addition, the resistor R5 in the present embodiment is divided into two resistors R5a and R5b, with the node formed by these resistors connected to the control input 14 by means of the resistor R12. When this input 14 is connected to the positive terminal of the battery, a portion of the battery voltage, for example, half of this voltage, occurs on resistor R12. When transistor N4 is open during the reverse, the voltage divider containing resistor R4 and resistor R5a provides tr. that part of the voltage across resistor R12 occurs at resistor k4. By appropriately selecting the resistors R4 and R5a, the transistor T2 can be opened with twice the battery voltage than when the transistor T2 opens with no signal at the signal input 14. This change in current to the jet is possible with a higher battery voltage than during normal using. This feature can be used to very quickly recharge used batteries. In addition, the present embodiment contains a light emitting diode D7 flashing with such a frequency as to give the impression of a continuously burning diode. The diode D7 thus works as a battery charge indicator.
    Figure 4 shows a third embodiment of the power scheme according to the invention, the identical parts being marked with the same digital references. The rate at which the primary current increases during the forward stroke interval, as a function of time, is proportional to the input voltage. As the input voltage increases, the value of the primary current at which the transistor T1 closes is, therefore, reachable faster. This leads to a high switching frequency in the power supply circuit, with the result that the average charge current increases with increasing input voltage. In order to keep the charging current as constant as possible, while the input voltage increases, the circuit is equipped with an input voltage compensation circuit. To this end, the Zener diode D4 from the circuit shown in Fig. 3 is replaced by a voltage control circuit, which reduces the voltage as the input voltage rises. This voltage control circuit includes a sequence of devices consisting of resistors R13 and R14, which are installed between the emitter transistors T4 and output 4 of resistor R1 and the node formed by them is connected to the base of transistor T5, whose collector is connected to resistor R14, the base - to the output 5 of the secondary winding N2 through a resistor RT5. During the forward stroke interval, a portion of the voltage on resistor R1 appears on resistor R14 through voltage divider R4, R13 and R14. and a part of the voltage on the secondary winding N2 appears on this resistor R14 through voltage divider R15, R14. When the voltage across the resistor R14 reaches the boundary voltage of the transistor T5, this transistor will open. The collector-emitter voltage is now equal to the base-emitter voltage of the T6 transistor multiplied by a factor determined by the resistance values of the resistors R13 and R.14. This voltage does not increase further with increasing voltage across resistor R1. As the input voltage rises, the voltage across the secondary winding N2 increases, causing an increase in voltage across resistor R14. In this way, it is achieved that with an increase in the input voltage, the latter across the resistor R14 reaches the limit emitter-base value for the transistor T5 when the values of the primary current decrease in such a way that, to increase the input voltage, the transistor T1 is closed at increasing values of the primary current . As a result, the average charge current becomes substantially independent of the input voltage.
    Fig. 5 shows a fourth embodiment of the power scheme according to the invention, the identical parts being marked by the same digital references as in Fig. 4. In this embodiment, resistor R15 is not connected to the positive terminal of the secondary winding N2 during the flyback interval, but it is connected to the positive terminal of the primary winding N1. It should be noted that the resistor R1.5 can alternately be connected to any other point of the circuit that is under voltage proportional to the input. In this embodiment, the node formed by resistors R5a and R5b is also connected to the base of transistor T6, the emitter of which is connected to the terminal of the resistor R5a far from the base, and the collector of which is connected to the resistor R5a from the terminal far from the terminal. In addition, the base of the transistor T6 is connected to the control input 14 via a resistor R12. When transistor T4 is in the conducting state, the voltage across the resistor R5b is higher than the boundary voltage of the transistor Tb so that this transistor is in the conducting state. The collector-emitter voltage of this transistor is set to a value equal to the product of the base-emitter voltage of the transistor TB and the factor determined by the resistance values of the resistors R5a and R5b. The difference between the voltage of the battery and the voltage across the transistor TB arises on the resistor R4 and determines the need for a change to the jet charge. By connecting terminal 14 to the emitter of the transistor TB, resistors R5a and R12 are installed in parallel. With an appropriate selection of the value of resistor R12 relative to the value of resistor R5b, the voltage across the transistor TB increases. This means that a smaller portion of the battery voltage will appear on resistor R4 than usual, and that terminal 14 will not carry a signal. As a result, the battery voltage at which the change to the jet charge is made will be greater than in the first case given.
    The first and second transistor switches may alternately contain composite transistors or other semiconductor switching elements. In addition, the first switching means and the input voltage compensation means can be constructed in other ways than those shown.
    权利要求:
    Claims (13)
    [1]
    Claim 1. Power circuit for charging a battery with charge current, in particular for an electric razor, comprising between the first and second power terminals: a first sequence of devices consisting of a primary winding of a transformer, a first transistor switch having a control input, a first resistor, and also a second sequence of devices consisting of a secondary winding and a first diode, this second series of devices containing terminals for connecting a battery, a positive feedback circuit between a node formed by the secondary winding and the first diode, and the control input of the first transistor switch, this positive feedback circuit containing a sequence of devices consisting of a second resistor and a first capacitor that is far from the second resistor and the output of the first capacitor is connected to a Zener diode
    means for turning off the first transistor switch at a certain voltage on the first resistor, which contains the first input connected to the output of the first resistor closest to the first transistor switch, the second input connected to the far end of the first transistor switch from the first transistor switch of the first resistor . and an output which is connected to the control input of the first transistor switch, a second switching means for replacing the charging current with a jet charging current above a certain limit
    5 voltage, characterized in that, in order to increase operational reliability, the anode of the Zener diode is connected to one output of the first resistor, the second switching means containing a sequence of devices consisting of a third resistor, a second transistor switch having a control input, and the fourth resistor installed between the first input of the switching means
    5 and the second power terminal, the control input of the second transistor switch is connected to the node formed by the second resistor and the first capacitor, the third diode is installed parallel to the second resistor.
    0
    [2]
    2. The circuit according to claim 1, characterized in that a sequence of devices consisting of the fifth and sixth resistors is connected between the second input of the switching means and the node formed by the second resistor and the first capacitor, the control input of the second transistor switch is connected to the node formed by the fifth and sixth resistors.
    [3]
    3. The circuit according to claim 2, different from 0. that the fifth resistor is variable.
    [4]
    4. The circuit according to claim 2 or 3, characterized in that the fourth resistor is formed by a sequence of devices consisting
    5 of the two resistors, the node formed by them is connected via the seventh resistor to the control input for receiving a voltage increase control signal, at which the charge is replaced
    0 current per jet charge current.
    [5]
    5. The circuit according to claim 4, wherein in order to increase the switching voltage the seventh resistor is connected to the positive terminal of the battery.
    five
    [6]
    6. The circuit according to claim 4, characterized in that the node formed by two resistors is connected to the base of the third transistor, the collector and emitter of which is connected to the terminals of the resistors far from the node, moreover, to increase the turn-off voltage, the seventh resistor is connected to the third transistor ,
    [7]
    7. The circuit according to claims 1-6, characterized in that the second input of the switching amplifier is connected to the far end of the first transistor switch of the first resistor through a voltage source for supplying a reference voltage, which decreases with increasing input voltage.
    [8]
    8. The circuit according to claim 7, wherein the reference voltage source comprises a sequence of devices consisting of an eighth and a ninth resistors, the node formed by them being connected to a voltage terminal set to hold the voltage generated by the tenth resistor proportional to the input, and the base of the fourth transistor, the collector and the emitter of which are connected to the terminals of the eighth and ninth resistors far from the node, respectively.
    [9]
    9. The circuit according to claim 8, wherein the voltage terminal is formed by a node between the secondary and the first diode.
    [10]
    10. The circuit according to claim. 8, characterized in that the voltage terminal is formed
    0
    five
    via an input terminal connected to the primary winding.
    [11]
    11. The circuit according to claims 1-10, wherein the first switching means includes a fifth transistor, the emitter of which is connected to the first input, the base to the second input, and the collector to the second power terminal by means of a sequence of devices of the eleventh and twelfth resistors, with the node formed by the eleventh and twelfth resistors connected to the base of the sixth transistor, the collector of which is connected to the control input of the first transistor switch and through the second capacitor to the second input of the first switching means.
    [12]
    12. Circuit diagram 1-11, characterized in that a light emitting diode is installed between the control input of the first transistor switch and the positive terminal of the battery.
    [13]
    13. The circuit in accordance with claim 11, wherein the thirteenth resistor is installed in series with the light-emitting diode.
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    同族专利:
    公开号 | 公开日
    CA2009738A1|1990-08-14|
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    US4965506A|1990-10-23|
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    引用文献:
    公开号 | 申请日 | 公开日 | 申请人 | 专利标题
    EP0030026B2|1979-11-29|1989-01-25|Klaus Becker|Circuit arrangement for the regular supply to a user|
    US4376263A|1980-11-06|1983-03-08|Braun Aktiengesellschaft|Battery charging circuit|
    DE3218594A1|1982-05-17|1983-12-22|Braun Ag, 6000 Frankfurt|ELECTRONIC SWITCHING POWER SUPPLY|
    NL8500154A|1985-01-22|1986-08-18|Koninkl Philips Electronics Nv|SELF-OSCILLATING POWER SUPPLY.|
    NL8503479A|1985-12-18|1987-07-16|Philips Nv|POWER SUPPLY.|
    DE3618221C1|1986-05-30|1993-02-11|Braun Ag|Switching power supply with a great clocked DC converter|DE4122544C1|1991-07-08|1992-07-16|Braun Ag, 6000 Frankfurt, De|
    DE4212041A1|1992-04-10|1993-10-14|Braun Ag|Electronic switching power supply|
    DE4241065C1|1992-12-05|1994-03-31|Braun Ag|Electronic switching power supply for feeding an accumulator|
    US5610804A|1994-06-20|1997-03-11|Tdk Corporation|Power supply with dual energy transfer circuits for power factor correction|
    CN1056949C|1995-11-27|2000-09-27|皇家菲利浦电子有限公司|Power supply circuit|
    WO1997020379A1|1995-11-27|1997-06-05|Philips Electronics N.V.|Power-supply circuit|
    CN1077349C|1995-11-27|2002-01-02|皇家菲利浦电子有限公司|Power-supply circuit|
    DE19609140A1|1996-03-08|1997-09-18|Nokia Mobile Phones Ltd|Charging circuit|
    FR2786338B1|1998-11-24|2001-02-09|St Microelectronics Sa|CONTINUOUS HIGH AND LOW VOLTAGE SUPPLY|
    US6492792B1|2002-05-26|2002-12-10|Motorola, Inc|Battery trickle charging circuit|
    WO2005122372A1|2004-06-07|2005-12-22|Salcomp Oyj|Method and circuit arrangement for optimising maximum current limitation in the primary switch of a switched-mode power supply, and a power supply|
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    CN103779906B|2014-01-24|2017-02-01|无锡中感微电子股份有限公司|Charge management device and system|
    法律状态:
    优先权:
    申请号 | 申请日 | 专利标题
    NL8900360|1989-02-14|
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